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| Order this document by UAA2016/D UAA2016 Zero Voltage Switch Power Controller The UAA2016 is designed to drive triacs with the Zero Voltage technique which allows RFI-free power regulation of resistive loads. Operating directly on the AC power line, its main application is the precision regulation of electrical heating systems such as panel heaters or irons. A built-in digital sawtooth waveform permits proportional temperature regulation action over a 1C band around the set point. For energy savings there is a programmable temperature reduction function, and for security a sensor failsafe inhibits output pulses when the sensor connection is broken. Preset temperature (i.e. defrost) application is also possible. In applications where high hysteresis is needed, its value can be adjusted up to 5C around the set point. All these features are implemented with a very low external component count. * Zero Voltage Switch for Triacs, up to 2.0 kW (MAC212A8) ZERO VOLTAGE SWITCH POWER CONTROLLER SEMICONDUCTOR TECHNICAL DATA 8 1 * * * * * * * Direct AC Line Operation Proportional Regulation of Temperature over a 1C Band Programmable Temperature Reduction Preset Temperature (i.e. Defrost) Sensor Failsafe Adjustable Hysteresis Low External Component Count P SUFFIX PLASTIC PACKAGE CASE 626 8 1 D SUFFIX PLASTIC PACKAGE CASE 751 (SO-8) PIN CONNECTIONS Vref 1 8 7 6 5 (Top View) Sync VCC Output VEE Representative Block Diagram Failsafe 3 Sense Input + - Sampling Full Wave Logic Internal Reference Hys. Adj. 2 UAA2016 Pulse Amplifier 6 Output Sensor 3 Temp. Reduc. 4 4 Temperature Reduction + + + 7 +VCC 1/2 4-Bit DAC Hysteresis Adjust Voltage Reference 2 Synchronization Supply Voltage ORDERING INFORMATION Device Operating Temperature Range TA = - 20 to +85C Package SO-8 Plastic DIP 1 11-Bit Counter UAA2016D UAA2016P 8 Sync 5 VEE (c) Motorola, Inc. 1999 Rev 6 MOTOROLA ANALOG IC DEVICE DATA 1 UAA2016 MAXIMUM RATINGS (Voltages referenced to Pin 7) Rating Supply Current (IPin 5) Non-Repetitive Supply Current (Pulse Width = 1.0 s) AC Synchronization Current Pin Voltages Symbol ICC ICCP Isync VPin 2 VPin 3 VPin 4 VPin 6 IPin 1 IO PD RJA TA Value 15 200 3.0 0; Vref 0; Vref 0; Vref 0; VEE 1.0 150 625 100 - 20 to + 85 Unit mA mA mA V Vref Current Sink Output Current (Pin 6) (Pulse Width < 400 s) Power Dissipation Thermal Resistance, Junction-to-Air Operating Temperature Range mA mA mW C/W C ELECTRICAL CHARACTERISTICS (TA = 25C, VEE = -7.0 V, voltages referred to Pin 7, unless otherwise noted.) Characteristic Supply Current (Pins 6, 8 not connected) (TA = - 20 to + 85C) Stabilized Supply Voltage (Pin 5) Reference Voltage (Pin 1) Output Pulse Current (TA = - 20 to + 85C) (Rout = 60 W, VEE = - 8.0 V) Output Leakage Current (Vout = 0 V) Output Pulse Width (TA = - 20 to + 85C) (Note 1) (Mains = 220 Vrms, Rsync = 220 k) Comparator Offset (Note 5) Sensor Input Bias Current Sawtooth Period (Note 2) Sawtooth Amplitude (Note 6) Temperature Reduction Voltage (Note 3) (Pin 4 Connected to VCC) Internal Hysteresis Voltage (Pin 2 Not Connected) Additional Hysteresis (Note 4) (Pin 2 Connected to VCC) Failsafe Threshold (TA = - 20 to + 85C) (Note 7) (ICC = 2.0 mA) Symbol ICC -- VEE Vref IO 90 IOL TP 50 Voff IIB TS AS VTR 280 VIH -- VH 280 VFSth 180 350 -- 420 300 mV 10 -- mV 350 420 mV -10 -- -- 50 -- -- -- 40.96 70 100 +10 0.1 -- 90 mV A sec mV mV -- 100 -- 130 10 A s -10 - 6.5 0.9 - 9.0 - 5.5 1.5 - 8.0 - 4.5 V V mA Min Typ Max Unit mA NOTES: 1. Output pulses are centered with respect to zero crossing point. Pulse width is adjusted by the value of Rsync. Refer to application curves. 2. The actual sawtooth period depends on the AC power line frequency. It is exactly 2048 times the corresponding period. For the 50 Hz case it is 40.96 sec. For the 60 Hz case it is 34.13 sec. This is to comply with the European standard, namely that 2.0 kW loads cannot be connected or removed from the line more than once every 30 sec. 3. 350 mV corresponds to 5C temperature reduction. This is tested at probe using internal test pad. Smaller temperature reduction can be obtained by adding an external resistor between Pin 4 and VCC. Refer to application curves. 4. 350 mV corresponds to a hysteresis of 5C. This is tested at probe using internal test pad. Smaller additional hysteresis can be obtained by adding an external resistor between Pin 2 and VCC. Refer to application curves. 5. Parameter guaranteed but not tested. Worst case 10 mV corresponds to 0.15C shift on set point. 6. Measured at probe by internal test pad. 70 mV corresponds to 1C. Note that the proportional band is independent of the NTC value. 7. At very low temperature the NTC resistor increases quickly. This can cause the sensor input voltage to reach the failsafe threshold, thus inhibiting output pulses; refer to application schematics. The corresponding temperature is the limit at which the circuit works in the typical application. By setting this threshold at 0.05 Vref, the NTC value can increase up to 20 times its nominal value, thus the application works below - 20C. 2 MOTOROLA ANALOG IC DEVICE DATA UAA2016 Figure 1. Application Schematic S2 RS S1 Rdef R2 R1 R3 3 Sense Input 4 Failsafe + - Sampling Full Wave Logic UAA2016 MAC212A8 Pulse Amplifier 6 Rout Output 220 Vac Load 7 +VCC CF NTC Temp. Red. + + + 1/2 Internal Reference 4-Bit DAC 2 HysAdj 11-Bit Counter 1 Vref Sync Rsync 8 VEE RS 5 Synchronization Supply Voltage APPLICATION INFORMATION (For simplicity, the LED in series with Rout is omitted in the following calculations.) Triac Choice and Rout Determination Depending on the power in the load, choose the triac that has the lowest peak gate trigger current. This will limit the output current of the UAA2016 and thus its power consumption. Use Figure 4 to determine Rout according to the triac maximum gate current (IGT) and the application low temperature limit. For a 2.0 kW load at 220 Vrms, a good triac choice is the Motorola MAC212A8. Its maximum peak gate trigger current at 25C is 50 mA. For an application to work down to - 20C, Rout should be 60 . It is assumed that: IGT(T) = IGT(25C) exp (-T/125) with T in C, which applies to the MAC212A8. The load current is then: I Load + (Vrms 2 sin(2pft)-V TM )R L where VTM is the maximum on state voltage of the triac, f is the line frequency. Set ILoad = ILatch for t = TP/2 to calculate TP. Figures 6 and 7 give the value of TP which corresponds to the higher of the values of IHold and ILatch, assuming that VTM = 1.6 V. Figure 8 gives the Rsync that produces the corresponding TP. RSupply and Filter Capacitor With the output current and the pulse width determined as above, use Figures 9 and 10 to determine RSupply, assuming that the sinking current at Vref pin (including NTC bridge current) is less than 0.5 mA. Then use Figure 11 and 12 to determine the filter capacitor (CF) according to the ripple desired on supply voltage. The maximum ripple allowed is 1.0 V. Temperature Reduction Determined by R1 (Refer to Figures 13 and 14.) Output Pulse Width, Rsync The pulse with TP is determined by the triac's IHold, ILatch together with the load value and working conditions (frequency and voltage): Given the RMS AC voltage and the load power, the load value is: RL = V2rms/POWER MOTOROLA ANALOG IC DEVICE DATA 3 UAA2016 Figure 2. Comparison Between Proportional Control and ON/OFF Control Overshoot Proportional Band Room Temperature T (C) Time (minutes, Typ.) Time (minutes, Typ.) Heating Power P(W) Time (minutes, Typ.) Proportional Temperature Control D Reduced Overshoot D Good Stability Time (minutes, Typ.) ON/OFF Temperature Control D Large Overshoot D Marginal Stability Figure 3. Zero Voltage Technique TP is centered on the zero-crossing. TP AC Line Waveform IHold ILatch Gate Current Pulse T R sync + 14 xVrms )2 7x pf 10 P 5 (s) f = AC Line Frequency (Hz) Vrms = AC Line RMS Voltage (V) Rsync = Synchronization Resistor () 4 MOTOROLA ANALOG IC DEVICE DATA UAA2016 CIRCUIT FUNCTIONAL DESCRIPTION Power Supply (Pin 5 and Pin 7) The application uses a current source supplied by a single high voltage rectifier in series with a power dropping resistor. An integrated shunt regulator delivers a VEE voltage of - 8.6 V with respect to Pin 7. The current used by the total regulating system can be shared in four functional blocks: IC supply, sensing bridge, triac gate firing pulses and zener current. The integrated zener, as in any shunt regulator, absorbs the excess supply current. The 50 Hz pulsed supply current is smoothed by the large value capacitor connected between Pins 5 and 7. Temperature Sensing (Pin 3) The actual temperature is sensed by a negative temperature coefficient element connected in a resistor divider fashion. This two element network is connected between the ground terminal Pin 5 and the reference voltage - 5.5 V available on Pin 1. The resulting voltage, a function of the measured temperature, is applied to Pin 3 and internally compared to a control voltage whose value depends on several elements: Sawtooth, Temperature Reduction and Hysteresis Adjust. (Refer to Application Information.) Temperature Reduction For energy saving, a remotely programmable temperature reduction is available on Pin 4. The choice of resistor R1 connected between Pin 4 and VCC sets the temperature reduction level. Comparator When the positive input (Pin 3) receives a voltage greater than the internal reference value, the comparator allows the triggering logic to deliver pulses to the triac gate. To improve the noise immunity, the comparator has an adjustable hysteresis. The external resistor R3 connected to Pin 2 sets the hysteresis level. Setting Pin 2 open makes a 10 mV hysteresis level, corresponding to 0.15C. Maximum hysteresis is obtained by connecting Pin 2 to VCC. In that case the level is set at 5C. This configuration can be useful for low temperature inertia systems. Sawtooth Generator In order to comply with European norms, the ON/OFF period on the load must exceed 30 seconds. This is achieved by an internal digital sawtooth which performs the proportional regulation without any additional component. The sawtooth signal is added to the reference applied to the comparator negative input. Figure 2 shows the regulation improvement using the proportional band action. Noise Immunity The noisy environment requires good immunity. Both the voltage reference and the comparator hysteresis minimize the noise effect on the comparator input. In addition the effective triac triggering is enabled every 1/3 sec. Failsafe Output pulses are inhibited by the "failsafe" circuit if the comparator input voltage exceeds the specified threshold voltage. This would occur if the temperature sensor circuit is open. Sampling Full Wave Logic Two consecutive zero-crossing trigger pulses are generated at every positive mains half-cycle. This ensures that the number of delivered pulses is even in every case. The pulse length is selectable by Rsync connected on Pin 8. The pulse is centered on the zero-crossing mains waveform. Pulse Amplifier The pulse amplifier circuit sinks current pulses from Pin 6 to VEE. The minimum amplitude is 70 mA. The triac is then triggered in quadrants II and III. The effective output current amplitude is given by the external resistor Rout. Eventually, an LED can be inserted in series with the Triac gate (see Figure 1). 200 R out , OUTPUT RESISTOR ( ) 180 160 140 120 100 80 60 40 20 TA = -10C 30 40 50 IGT, TRIAC GATE CURRENT SPECIFIED AT 25C (mA) 60 TA = - 20C TA = +10C TA = 0C I Out(min) , MINIMUM OUTPUT CURRENT (mA) Figure 4. Output Resistor versus Triac Gate Current Figure 5. Minimum Output Current versus Output Resistor 100 80 60 40 20 0 40 60 80 100 120 140 160 Rout, OUTPUT RESISTOR () 180 200 TA = - 20C TA = + 85C MOTOROLA ANALOG IC DEVICE DATA 5 UAA2016 Figure 6. Output Pulse Width versus Maximum Triac Latch Current 120 TP, OUTPUT PULSE WIDTH ( s) 100 80 110 Vrms 60 220 Vrms 40 20 0 20 30 40 50 ILatch(max), MAXIMUM TRIAC LATCH CURRENT (mA) 10 60 TP, OUTPUT PULSE WIDTH ( s) F = 50 Hz 2.0 kW Loads VTM = 1.6 V TA = 25C 120 100 80 60 220 Vrms 40 20 0 10 20 30 40 50 ILatch(max), MAXIMUM TRIAC LATCH CURRENT (mA) 60 F = 50 Hz 1.0 kW Loads VTM = 1.6 V TA = 25C 110 Vrms Figure 7. Output Pulse Width versus Maximum Triac Latch Current R sync , SYNCHRONIZATION RESISTOR (k ) 400 F = 50 Hz 300 220 Vrms 200 110 Vrms R Supply , MAXIMUM SUPPLY RESISTOR (k ) Figure 8. Synchronization Resistor versus Output Pulse Width Figure 9. Maximum Supply Resistor versus Output Current 60 V = 220 Vrms F = 50 Hz 50 TP = 50 s 40 100 s 30 150 s 200 s 0 25 50 75 IO, OUTPUT CURRENT (mA) 100 100 0 20 40 60 80 TP, OUTPUT PULSE WIDTH (s) 100 20 R Supply, MAXIMUM SUPPLY RESISTOR (k ) C F(min), MINIMUM FILTER CAPACITOR ( F) Figure 10. Maximum Supply Resistor versus Output Current 30 V = 110 Vrms F = 50 Hz 25 TP = 50 s 100 s 15 150 s 200 s 0 25 50 75 IO, OUTPUT CURRENT (mA) 100 Figure 11. Minimum Filter Capacitor versus Output Current 90 Ripple = 1.0 Vp-p F = 50 Hz 80 70 60 50 TP = 50 s 40 0 20 40 60 IO, OUTPUT CURRENT (mA) 80 100 200 s 150 s 100 s 20 10 6 MOTOROLA ANALOG IC DEVICE DATA UAA2016 Figure 12. Minimum Filter Capacitor versus Output Current TR , TEMPERATURE REDUCTION ( C) 180 160 140 120 100 TP = 50 s 80 0 20 40 60 IO, OUTPUT CURRENT (mA) 80 100 Ripple = 0.5 Vp-p F = 50 Hz 200 s 150 s 100 s 7.0 Setpoint = 20C 6.0 5.0 4.0 3.0 2.0 1.0 0 0 10 20 30 40 50 60 70 80 90 R1, TEMPERATURE REDUCTION RESISTOR (k) 100 10 k NTC 100 k NTC C F(min), MINIMUM FILTER CAPACITOR ( F) Figure 13. Temperature Reduction versus R1 Figure 14. Temperature Reduction versus Temperature Setpoint TR , TEMPERATURE REDUCTION ( C) 6.0 5.6 10 k NTC 5.2 4.8 100 k NTC 4.4 4.0 10 4 RDEF /(NOMINAL NTC VALUE) RATIO R1 = 0 Figure 15. RDEF versus Preset Temperature 100 k NTC 3 10 k NTC 2 1 14 18 22 26 TS, TEMPERATURE SETPOINT (C) 30 0 0 5 10 15 20 25 TDEF, PRESET TEMPERATURE (C) 30 V H , COMPARATOR HYSTERESIS VOLTAGE (V) Figure 16. RS + R2 versus Preset Setpoint ( R S + R 2 /(NOMINAL NTC VALUE) RATIO 8 TDEF = 4C 6 Figure 17. Comparator Hysteresis versus R3 0.5 0.4 0.3 0.2 0.1 0 4 10 k NTC RDEF = 29 k 100 k NTC RDEF = 310 k 14 18 22 26 30 TS, TEMPERATURE SETPOINT (C) 34 2 0 10 0 100 200 300 R3, HYSTERESIS ADJUST RESISTOR (k) 400 MOTOROLA ANALOG IC DEVICE DATA 7 UAA2016 OUTLINE DIMENSIONS P SUFFIX PLASTIC PACKAGE CASE 626-05 ISSUE K -B- 1 4 8 5 NOTES: 1. DIMENSION L TO CENTER OF LEAD WHEN FORMED PARALLEL. 2. PACKAGE CONTOUR OPTIONAL (ROUND OR SQUARE CORNERS). 3. DIMENSIONING AND TOLERANCING PER ANSI Y14.5M, 1982. DIM A B C D F G H J K L M N MILLIMETERS MIN MAX 9.40 10.16 6.10 6.60 3.94 4.45 0.38 0.51 1.02 1.78 2.54 BSC 0.76 1.27 0.20 0.30 2.92 3.43 7.62 BSC --- 10_ 0.76 1.01 INCHES MIN MAX 0.370 0.400 0.240 0.260 0.155 0.175 0.015 0.020 0.040 0.070 0.100 BSC 0.030 0.050 0.008 0.012 0.115 0.135 0.300 BSC --- 10_ 0.030 0.040 F NOTE 2 -A- L C -T- SEATING PLANE J N D K M M H G 0.13 (0.005) TA M B M -A- 8 5 D SUFFIX PLASTIC PACKAGE CASE 751-05 ISSUE N (SO-8) -B- 4X P 0.25 (0.010) M 1 4 B M NOTES: 1. DIMENSIONING AND TOLERANCING PER ANSI Y14.5M, 1982. 2. CONTROLLING DIMENSION: MILLIMETER. 3. DIMENSIONS A AND B DO NOT INCLUDE MOLD PROTRUSION. 4. MAXIMUM MOLD PROTRUSION 0.15 (0.006) PER SIDE. 5. DIMENSION D DOES NOT INCLUDE DAMBAR PROTRUSION. ALLOWABLE DAMBAR PROTRUSION SHALL BE 0.127 (0.005) TOTAL IN EXCESS OF THE D DIMENSION AT MAXIMUM MATERIAL CONDITION. DIM A B C D F G J K M P R MILLIMETERS MIN MAX 4.80 5.00 3.80 4.00 1.35 1.75 0.35 0.49 0.40 1.25 1.27 BSC 0.18 0.25 0.10 0.25 0_ 7_ 5.80 6.20 0.25 0.50 INCHES MIN MAX 0.189 0.196 0.150 0.157 0.054 0.068 0.014 0.019 0.016 0.049 0.050 BSC 0.007 0.009 0.004 0.009 0_ 7_ 0.229 0.244 0.010 0.019 G C -T- 8X SEATING PLANE R X 45 _ F D 0.25 (0.010) M K TB M_ S J S A Motorola reserves the right to make changes without further notice to any products herein. Motorola makes no warranty, representation or guarantee regarding the suitability of its products for any particular purpose, nor does Motorola assume any liability arising out of the application or use of any product or circuit, and specifically disclaims any and all liability, including without limitation consequential or incidental damages. "Typical" parameters which may be provided in Motorola data sheets and/or specifications can and do vary in different applications and actual performance may vary over time. All operating parameters, including "Typicals" must be validated for each customer application by customer's technical experts. Motorola does not convey any license under its patent rights nor the rights of others. Motorola products are not designed, intended, or authorized for use as components in systems intended for surgical implant into the body, or other applications intended to support or sustain life, or for any other application in which the failure of the Motorola product could create a situation where personal injury or death may occur. Should Buyer purchase or use Motorola products for any such unintended or unauthorized application, Buyer shall indemnify and hold Motorola and its officers, employees, subsidiaries, affiliates, and distributors harmless against all claims, costs, damages, and expenses, and reasonable attorney fees arising out of, directly or indirectly, any claim of personal injury or death associated with such unintended or unauthorized use, even if such claim alleges that Motorola was negligent regarding the design or manufacture of the part. Motorola and are registered trademarks of Motorola, Inc. Motorola, Inc. is an Equal Opportunity/Affirmative Action Employer. Mfax is a trademark of Motorola, Inc. How to reach us: USA / EUROPE / Locations Not Listed: Motorola Literature Distribution; P.O. Box 5405, Denver, Colorado 80217. 1-303-675-2140 or 1-800-441-2447 Customer Focus Center: 1-800-521-6274 MfaxTM: RMFAX0@email.sps.mot.com - TOUCHTONE 1-602-244-6609 ASIA/PACIFIC: Motorola Semiconductors H.K. Ltd.; Silicon Harbour Centre, Motorola Fax Back System - US & Canada ONLY 1-800-774-1848 2, Dai King Street, Tai Po Industrial Estate, Tai Po, N.T., Hong Kong. - http://sps.motorola.com/mfax/ 852-26629298 HOME PAGE: http://motorola.com/sps/ JAPAN: Motorola Japan Ltd.; SPD, Strategic Planning Office, 141, 4-32-1 Nishi-Gotanda, Shinagawa-ku, Tokyo, Japan. 81-3-5487-8488 8 UAA2016/D MOTOROLA ANALOG IC DEVICE DATA |
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